Method of calibrating impedance measurements of a battery

ABSTRACT

A method of calibration is described that simplifies the measurement of battery impedance conducted in-situ while determining battery state-of-health. A single shunt measurement with a known Sum of Sines (SOS) current, at the desired frequency spread and known root mean squared (RMS) current is used to create a calibration archive. A calibration selected from this archive is used to calibrate an impedance measurement made on the battery.

This application claims benefit of U.S. Provisional Application No.62/326,923, filed Apr. 25, 2016, and U.S. Provisional Application No.62/331,730, filed May 4, 2016, the disclosures of which are herebyincorporated by reference in their entirety including all figures,tables and drawings.

BACKGROUND OF THE INVENTION

Batteries and other electrical energy storage devices have become widelyused in not only military, space, and commercial applications but alsoin domestic applications. Therefore, it has become even more importantto be able to efficiently and effectively obtain an accurate estimationof the battery's state-of-health. While voltage, current, andtemperature may be used to gauge the remaining capacity of a battery, incritical applications it is also necessary to know impedance and powercapability to get an accurate picture of battery health. Ideally, anymeasurement of battery health is done in-situ and has minimal impact onthe battery. A great deal of work has been conducted to test batteryimpedance without effecting battery status. This work is documented in,for example, U.S. Pat. Nos. 7,688,036; 7,395,163 B1; 7,675,293 B2;8,150,643 B1; 8,352,204 B2; 8,762,109 B2; 8,868,363 B2; and 9,244,130B2, and U.S. Published Patent Application Nos. 2011/0270559 A1;2014/0358462 A1; and 2017/0003354 A1. Each variation of the methodsdescribed in these documents improve the process of assessing batteryhealth by, for example, increasing resolution. Recently, a method fortesting battery impedance has been described that increases theresolution of a known system by a factor of ten. Key features of thishigh resolution method involve a new algorithm, auto-ranging to obtainthe optimum level of excitation current, and increased preamplifiergain. The method also required an additional measurement channel thatcaptures time records of the Sum-Of-Sines (SOS) current in addition tothe SOS voltage from the test battery.

Although the above-methods have refined this important process, animproved method for calibration that will greatly simplify thecalibration process and eliminate the extra measurement channel neededfor some methods is still needed.

All patents, patent applications, provisional patent applications andpublications referred to or cited herein, are incorporated by referencein their entirety to the extent they are not inconsistent with theteachings of the specification.

SUMMARY OF THE INVENTION

The invention involves an improved method of calibrating impedancemeasurements of a battery. The method needs only a single measurementwith a known Sum of Sines (SOS) current, at the desired frequency spreadand known root mean squared (RMS) current.

BRIEF DESCRIPTION OF THE SEVERAL VIEWS OF THE DRAWINGS

FIG. 1 shows the single shunt calibration of a test cell at 500 mA usingthe method of the subject invention.

FIG. 2 shows the single shunt calibration of a test cell with RMScurrent scale 500 mA down to 250 mA using the method of the subjectinvention.

FIG. 3 shows the single shunt calibration of a test cell with RMScurrent scale 500 mA down to 125 mA using the method of the subjectinvention.

FIG. 4 shows the single shunt calibration of a test cell with RMScurrent scale 500 mA down to 62.5 mA using the method of the subjectinvention.

FIG. 5 shows a single shunt calibration with Solatron EIS of a test cellusing the method of the subject invention.

FIG. 6 shows a single shunt calibration with Solatron EIS of a test cellusing the method of the subject invention.

FIG. 7 shows a single shunt calibration with Solatron EIS of a test cellusing the method of the subject invention).

FIG. 8 shows a lead acid battery measured at 62.5 mA and 15 frequencySOS showing 18 to 15 frequency and 500 mA to 62.5 mA RMS current andfrequency scaling.

FIG. 9 shows a lead acid battery measured at 125 mA RMS SOS showing 18to 15 frequency and 500 mA to 125 mA RMS current scaling and frequencyscaling.

FIG. 10 shows splining the calibration 14 frequencies in octavesdownward from 1000 Hz calibrated with 15 frequencies in octaves from 0.1Hz to 1638.4 Hz.

FIG. 11A demonstrates saturation tolerance time CTC algorithm with a 12V lead acid car battery and shows the unclipped battery time record.

FIG. 11B demonstrates saturation tolerance time CTC algorithm with a 12V lead acid car battery and shows the unclipped TCTC with baseline HCSDspectrum.

FIG. 11C demonstrates saturation tolerance time CTC algorithm with a 12V lead acid car battery and shows the clipped battery time record.

FIG. 11D demonstrates saturation tolerance time CTC algorithm with a 12V lead acid car battery and shows the clipped spectrum with baselineHCSD spectrum.

FIG. 12A demonstrates saturation tolerance TCTC algorithm with a Lithiumion battery and shows the unclipped battery time record.

FIG. 12B demonstrates saturation tolerance TCTC algorithm with a Lithiumion battery and shows the unclipped TCTC with baseline HCSD spectrum.

FIG. 12C demonstrates saturation tolerance TCTC algorithm with a Lithiumion battery and shows the clipped battery time record.

FIG. 12D demonstrates saturation tolerance TCTC algorithm with a Lithiumion battery and shows the clipped spectrum with baseline HCSD spectrum.

FIG. 13 is a block flow diagram of a method for generating a measure ofimpedance of a test device.

DETAILED DESCRIPTIONS OF THE INVENTION

The method of the subject invention is involves single shunt calibration(SSC) that applies to all generations of (Impedance Measurement Box)IMB. The subject method simplifies use of the IMB to assess batteryhealth. The Idaho National Laboratory (INL) has described the design andconstruction of the IMB in numerous patent documents (see, for example,U.S. Pat. Nos. 7,688,036; 7,395,163 B1; 7,675,293 B2; 8,150,643 B1;8,352,204 B2; 8,762,109 B2; 8,868,363 B2; and 9,244,130 B2, and U.S.Published Patent Application Nos. 2011/0270559 A1; 2014/0358462 A1; and2017/0003354 A1). Spectrum algorithms used in the implementation arealso described in the above patent documents and include, but are notlimited to, harmonic compensated synchronous detection (HCSD), fastsummation transformation (FST), generalized fast summationtransformation (GFST), frequency cross talk compensation (FCTC), timecross talk compensation (TCTC), harmonic orthogonal synchronoustransformation (HOST). Each of these spectrum algorithms are specialcases of a rapid Fourier Transform that bring the measurement timerecord captured by the IMB measurement into the frequency domain at onlythe frequencies that were part of the IMB excitation signal to the testbattery. The calibration in the present generation 50V IMB (U.S. PatentApplication Publication No. 2014/0358462) is accomplished by acomplicated measurement scheme which uses 3 different shunts to generatecalibration constants that yield a very accurate measurement of theimpedance spectra from a test battery (Morrison, William. H., thesis,2012). In contrast, the claimed method requires only a singlemeasurement with a known Sum Of Sines (SOS) current, at the desiredfrequency spread and known RMS current.

As an example consider application to the 50V IMB (U.S. PatentApplication Publication No. 2014/0358462). With the present 50V IMB HCSDalgorithm system (U.S. Patent Application Publication No. 2014/0358462),the calibration for a given SOS frequency spread (octave harmonic short0.1 Hz to 1638.4 Hz or long 0.0125 Hz to 1638.4 Hz) and a given SOS RMScurrent, the measurement time record that is processed into thefrequency domain is typically one period of the lowest frequency. Aspart of the calibration the SOS current output is pre-emphasized tomitigate the IMB system frequency response. Additionally, the 3 shuntcalibration scheme computes gain and offset constants for both magnitudeand phase at each frequency. Equation 1 represents the time recordcaptured by the IMB from a measurement on a test battery.V _(B)(t)=I _(SOS)(t)*A _(S)(t)*Z _(B)(t)   (1)

Where:

-   -   I_(SOS)(t) the SOS current time record    -   A_(S)(t) is the measurement system impulse response    -   Z_(B)(t) is the test battery impedance impulse response

The * in Equation 1 is a convolution operation. Because of thecalibration pre-emphasis, I_(SOS)(t) is given by:

$\begin{matrix}{{I_{SOS}(t)} = {{RMS}\sqrt{\frac{2}{m}}{\sum\limits_{i = 1}^{m}{\sin\left( {\omega_{i}t} \right)}}}} & (2)\end{matrix}$

Where:

-   -   RMS is the RMS of the SOS current    -   m is the number of frequencies in the SOS    -   ω_(i) is the i^(th) radian frequency        Note that the RMS of a SOS signal is:

${RMS} = {\sqrt{\sum\limits_{i = 1}^{m}\left( {\frac{1}{T_{i}}{\int_{T_{i}}{\left( {V_{p}{\sin\left( {\omega_{i}t} \right)}} \right)^{2}\ d\; t}}} \right)} = {V_{P}\sqrt{\frac{m}{2}}}}$$V_{P} = {{RMS}\sqrt{\frac{2}{m}}}$Equations 1 and 2 brought into the frequency domain via the 50V IMB HCSDalgorithm (Morrison, William H., thesis, 2012) becomes:

$\begin{matrix}{{\overset{\rightarrow}{V}}_{Bi} = {{RMS}\sqrt{\frac{2}{m}}\left( {A_{Si}{\measuredangle\phi}_{Si}} \right)\left( {Z_{Bi}{\measuredangle\phi}_{Bi}} \right)}} & (3)\end{matrix}$

Where:

-   -   A_(Si)        ϕ_(Si) is the measurement system frequency response at the        i^(th) frequency    -   Z_(Bi)        ϕ_(Bi) is the desired battery impedance at the i^(th) frequency        The effect of calibration is to multiply Equation 3 by a        calibration constant given by:

$\begin{matrix}{{CAL}_{i} = \left( {{RMS}\sqrt{\frac{2}{m}}\left( {A_{Si}{\measuredangle\phi}_{Si}} \right)} \right)^{- 1}} & (4)\end{matrix}$

Clearly the calibration applied to Equation 3 results in the desiredbattery impedance and the 50V IMB has demonstrated this with greatsuccess via the 3 shunt magnitude calibration and the stepped phaseshift calibration both yielding gain offset calibration constants thatrepresent Equation 4 (Morrison, William H. thesis, 2012). Observe thatEquation 4 is a calibration constant that is a combination of SOScurrent pre-emphasis and magnitude phase calibration at each frequency.The subject method does everything in a single measurement with a singleshunt, single shunt calibration (SSC).

For the 50V IMB system the concept is very simple. The system willperform a spectrum measurement on a known non-inductive shunt forexample a 50 mOhm non-inductive calibration shunt (as shown in FIG. 13,Block B1). The SOS current is set to the high level, 500 mA RMS (asshown in FIG. 13, Block B2). The system must be configured for nopre-emphasis and no calibration (U.S. Patent Application Publication No.2014/0358462). As the 50V IMB uses the HCSD algorithm, either 18frequencies are selected, 0.0125 Hz to 1638.4 Hz or 15 frequencies 0.1Hz to 1638.4 Hz both in octave steps (as shown in FIG. 13, Block B3).The measurement is performed and processed via the HCSD algorithm toconvert the captured time record into the frequency domain (as shown inFIG. 13, Blocks B4 and B5 respectively). Then the complex results ateach frequency are normalized to the measurement shunt value and the SOSRMS current (as shown in FIG. 13, Block B6). These results are in factEquation 6 and are stored in a calibration file that when recalled canbe used to calibrate a battery impedance measurement with the samefrequency spread and different RMS current (as per Equation 9)(as shownin FIG. 13, Block B7).

For the single shunt calibration (SSC), we assume that single shunt usedis constant and independent of frequency over the frequency range of theIMB Additionally, all measurements are made without any pre-emphasis.Thus as a function of time the IMB measurement of that shunt V_(sHuNT)(RMS,iΔt) is given by Equation 5.V _(SHUNT)(RMS,iΔt)=V _(SOS)(RMS,iΔt)*H _(OUT)(t)*R _(SHUNT) *H_(IN)(iΔt)   (5)

Where

-   -   *: indicates the convolution operation    -   V_(SOS)(RMS,iΔt): is the computer generated signal to IMB        current drivers    -   H_(OUT)(t): is the current driver system response in time    -   iΔt: is the computer discrete time    -   R_(SHUNT): is the calibration shunt, ohms    -   H_(IN)(iΔt): is the IMB system input response in discrete time        Also as a function of time the 1 MB measurement of a test        battery is given by Equation 6.        V _(Meas)(RMS,iΔt)=V _(SOS)(RMS,iΔt)*H _(OUT) *Z _(BAT)(t)*H        _(IN)(iΔt)   (6)

Where:

Z_(BAT)(t) is the impedance impulse response of the battery as afunction of time.

For the SSC the time record of the shunt (Equation 5) is processed bythe HCSD algorithm of the IMB, normalized by R_(SHUNT) and stored ascalibration. Equation 7 illustrated the shunt time record brought intothe frequency domain at one of the SOS frequencies ω_(i).V _(SHUNT)(ω_(i))V _(SOS)(RMS,ω_(i))H _(OUT)(ω_(i))R _(SHUNT) H_(IN)(ωi)   (7)

Where:

-   -   ω_(i) is radians/sec        Note that the convolution operation in Equation 5 goes to        multiplication in Equation 7. The time record of the battery        given by Equation 6 when brought into the frequency domain at        one of the SOS frequencies ω_(i) is given by Equation 8.        V _(Meas)(ω_(i))=V _(SOS)(RMS,ω_(i))H _(OUT)(ω_(i))Z        _(BAT)(ω_(i))H _(IN)(ω_(i))   (8)

Performing division in the frequency domain the essence of calibrationis given by Equation 9.

$\begin{matrix}{{Z_{BAT}\left( \omega_{i} \right)} = {R_{SHUNT}\frac{{V_{SOS}\left( {{RMS},\omega_{i}} \right)}{H_{OUT}\left( \omega_{i} \right)}{Z_{BAT}\left( \omega_{i} \right)}{H_{IN}\left( \omega_{i} \right)}}{{V_{SOS}\left( {{RMS},\omega_{i}} \right)}{H_{OUT}\left( \omega_{i} \right)}R_{SHUNT}{H_{IN}\left( {i\;\Delta\; t} \right)}}}} & (9)\end{matrix}$

Thus the SSC is a collection of measurements of R_(SHUNT) atstandardized RMS currents and SOS frequency spreads brought into thefrequency domain by the HCSD algorithm. For the IMB there are 2standardized frequency ranges and 4 standardized RMS currents. Tocalibrate for this, results in 8 measurements with the single shunt forSSC which are performed fully automated with a single shunt hook-up. Avast improvement over the original manual 3 shunt calibration process.

Observe Equation 7, if in addition to being normalized to the shunt ifit were normalized also to the calibration RMS current it can be used asa calibration for any battery measurement RMS current by scaling it tothat measurement RMS current.

Example 1—Validation Using 50V IMB and RMS Current Scaling

The 50V IMB at Montana Tech of the University of Montana (Butte, Mont.)was used for initial testing. A long run frequency (0.0125 Hz to 1638.4Hz) domain calibration file was generated (via HCSD) with-out anycalibration or pre-emphasis at an SOS current of 500 mA and a 50 mOhmshunt (as shown in FIG. 13, Blocks B1-B7). It was normalized to the 50mOhm shunt and the RMS current. Time records of measurements (long runs,0.0125 Hz to 1638.4 Hz) were made and captured for Test Cell (TC) #3(Morrison, William H., thesis, 2012) at RMS currents of 500 mA, 250 mA,125 mA and 62.5 mA again without any pre-emphasis (as shown in FIG. 13,Blocks B8 and B9). All those Test Cell time records were post processedinto the frequency domain with the HCSD algorithm ((as shown in FIG. 13,Block B10). The frequency domain calibration was scaled to eachmeasurement current RMS ((as shown in FIG. 13, Block B11). Test cellmeasurements were made at all the different currents (of 62.5 mA, 125mA, 250 mA and 500 mA) and calibrated per Equation 9. The results areshown in FIGS. 1-4. The detected TC #3 spectra are plotted withElectro-chemical impedance spectroscopy (EIS) (Solartron Analytical,2012) data by INL on TC #3. The validity of the subject method isrealized by the degree of coincidence of the two plots. Like resultswere achieved when the subject method was applied to Test Cells #3, #5,and #7. Results demonstrating SSC with these test cells are plotted andshown in FIGS. 5-7.

These results show that 500 mA shunt data can reach all the way down the62.5 mA to capture the spectra of TC #3 and the results match closelywith INL EIS (Solartron Analytical, 2012) data for TC #3 (as shown inFIG. 13, Block B12). This means that for calibration all that is neededis frequency domain files of known shunt, known frequencies and thatfile will work on measurements with the same frequencies and differentknown current with good results. This is a significant enhancement tothe existing 50V IMB.

As stated previously, with the single shunt calibration, with standardRMS currents and standard frequency ranges, a calibration is fullyautomated with as few as 8 measurements. Never the less, that can bereduced to a single calibration measurement with frequency scaling andRMS current scaling. In examining Equation 5 for calibration it would benormalized to the calibration RMS current and the shunt value. Then fora calibration it would be scaled by the measurement RMS. Consider theRMS of an SOS:

$\begin{matrix}{{{RMS}({SOS})} = {\sqrt{\left( {\sum\limits_{M}\frac{V_{P}^{2}}{2}} \right)} = {V_{P}\sqrt{\frac{M}{2}}}}} & (10)\end{matrix}$

Where:

-   -   M is the number of frequencies    -   V_(P) is the peak voltage of the sine waves in the SOS        Thus given that a measurement frequency range is an octave        harmonic subset of a calibration frequency range the frequency        domain the subset of real and imaginary constants are selected        out and scaled per:

$\begin{matrix}{({Calibration}) \times \sqrt{\frac{M_{CAL}}{M_{MEAS}}} \times \frac{{RMS}_{MEAS}}{{RMS}_{CAL}}} & (11)\end{matrix}$

Example 2—Validation Test of Frequency and RMS Calibration Scaling

Small lead acid battery measured by IMB with 62.5 mA and 15 frequencySOS. IMB spectrum obtained with normal IMB calibration. Uncalibratedtime record post processed to the frequency domain and calibrated by an18 frequency 500 mA shunt time record brought to the frequency domainand scaled to 15 frequency and 62.5 mA RMS. Both spectra are given inFIG. 8. FIG. 9 shows the battery measured by IMB at 125 mA RMS SOS (asshown in FIG. 13, Block B13). These results support frequency and RMScurrent scaling for SSC.

Example 3—Negative Time to Reinforce the Assumption of Steady State

The fundamental assumption of all IMB data processing algorithms is thatthe system being measured is in steady state relative to all excitationfrequencies. Clearly this is in contradiction to the requirement ofperforming a rapid measurement. The IMB measurement technique is toexcite the test article with a sum of sinusoids with an excitation timerecord of no more than one period of the lowest frequency. Someresearchers using the IMB measurement concept (Waligo, A., 2016) haveresorted to using multiple periods of the lowest frequency in order tore-inforce this assumption. A better solution is “Negative Time” (NT),whereby the sum of sinusoids starting at time zero would all be zero butif one goes backwards in time for a fraction of the period of the lowestfrequency, then start the excitation there, this has been shown to workvery well to establish the steady state approximation (10% is typical)(as shown in FIG. 13, Block B14). This NT portion is either ignored ordiscarded from the captured voltage response (as shown in FIG. 13, BlockB15). Additionally, NT is also needed for shunt calibration as smoothingfilter in the IMB will need to be brought to steady state.

When a calibration is scaled the objective is to make V_(P) of ameasurement and calibration the same thus the frequency range could bekept standardized as subsets of the calibration frequency range. Neverthe less, for non-standard subsets, even non-octave harmonic subsetsprocessed via time or frequency CTC (U.S. Pat. No. 8,762,109) thetechnique of “cubic spline” (U.S. Pat. No. 8,868,363) will select outthe calibration constants and they will scale exactly as the aboverelationship (as shown in FIG. 13, Block B16). FIG. 10 shows spliningthe calibration of 14 frequencies in octaves downward from 1000 Hzcalibrated with 15 frequencies in octaves from 0.1 Hz to 1638.4 Hz (asshown in FIG. 13, Block B17).

Example 4—Application to Saturation Tolerant Time and Frequency CTC

A critical feature of the concept for a High Resolution ImpedanceMeasurement Box (HRIMB) is its ability to digitize signals where thevoltage level of the signal is near and occasionally beyond thesaturation level of the digitizer within the Data Acquisition system(DAQ). This capability of the HRIMB is realized by replacing the dataprocessing algorithm (HCSD Morrison, W. H., thesis, 2012)) with avariation of time or frequency CTC (U.S. Pat. No. 8,762,109) (TCTC,FCTC). This feature for these 2 algorithms is achieved by examining thecaptured voltage time record for saturation points (as shown in FIG. 13,Block B18), noting the exact times of saturation, deleting those pointsfrom the voltage time record (as shown in FIG. 13, Block B19), andcomputing the algorithm correction matrices at only the times fornon-saturation. This technique works for both TCTC and FCTC. Thesealgorithms will bring the time domain voltage measurements (withoccasional saturation) into the frequency domain but they must becalibrated to become impedance. This is achieved by retrieving anarchived time record of a single shunt measurement that has the exactfrequencies of the “to be calibrated voltage” measurement, has beennormalized to the measurement shunt and its RMS current. That timerecord is scaled to the RMS current of the “to be calibrated voltage”and the exact points of the saturation in “to be calibrated voltage”time record are deleted from this time record (as shown in FIG. 13,Block B20). It is then processed with the same correction matrices usedwith the “to be calibrated voltage” time record (as shown in FIG. 13,Block B21). The impedance at each frequency is the ratio of the “to becalibrated voltage” phasor to the calibration phasor. Note that ifdecimation was used on the time records in the application of TCTC orFCTC the same decimation must be applied to the calibration time record.Decimation is a technique of uniformly discarding data points from timerecords to speed up data processing for TCTC or FCTC. Depending on thetype of battery being tested it should be kept below X16 and should beapplied prior to deletion of saturated data points.

Demonstration of saturation tolerance Time CTC algorithm with a 12V leadacid car battery, 500 mA RMS SOS current, 15 frequencies (0.1 Hz to1638.4 Hz) plotted with the IMB HCSD measurement response is shown inFIG. 11. Simulated clipping was done by discarding all points in thetime record of the response above or below 0.17V. The algorithm wascalibrated by a time record of 15 frequencies and 500 mA RMS applied toa shunt. FIG. 11A is the battery voltage time record. FIG. 11B is thespectrum plotted without clipping plotted with the IMB HCSD spectrum.FIG. 11C shows the clipped at +/−0.17V battery voltage time record. FIG.11D shows the Time CTC clipped spectrum plotted with the baseline HCSDspectrum.

FIG. 12 shows a similar demonstration of time CTC clipping Li Ionbattery. An 18 frequency (0.0125 Hz to 1638.4 Hz) 500 mA RMS SOSmeasurement was made on an Li Ion battery and a 50.27 mOhm shunt.Clipping tolerance was demonstrated by the battery voltage response at+/−0.2V. The Time CTC results are plotted with the baseline HCSD IMBspectrum. FIG. 12A gives the unclipped battery voltage time record. FIG.12B gives the time CTC processing of FIG. 12A calibrated with the shunttime record plotted with the HCSD baseline spectrum. FIG. 12C gives the+/−0.2V clipped battery voltage time record plotted with the clippingadjusted shunt time record. FIG. 12D gives the time CTC clipped spectrumplotted with the baseline HCSD spectrum. All time CTC processing wasdone with a X16 decimation.

It is understood that the foregoing examples are merely illustrative ofthe present invention. Certain modifications of the articles and/ormethods may be made and still achieve the objectives of the invention.Such modifications are contemplated as within the scope of the claimedinvention.

The invention claimed is:
 1. A method, comprising: performing a shuntmeasurement with one non-inductive shunt value using an excitationsignal including a root mean squared current and a frequency range;capturing a response time record of said one non-inductive shunt undertest; transforming said response time record to a frequency domain;normalizing said response time record transformed to said frequencydomain to said one non-inductive shunt value; and recording saidresponse time record transformed to said frequency domain and normalizedto said non-inductive shunt value as a calibration record; exciting adevice under test using said excitation signal including said at leastone RMS current level and said frequency range; capturing a responsetime record of said device under test; transforming said time record ofsaid device under test to said frequency domain; applying saidcalibration record to said response time record of said device undertest; and generating a measurement of said device under test.
 2. Themethod of claim 1, wherein said root mean squared current levelcomprises only a high range root mean squared current level; and scalingsaid measurement of said high range root mean square current level. 3.The method of claim 2, further comprising: performing said shuntmeasurement with one non-inductive shunt value using an excitationsignal including at least one the root mean squared current and each ofa plurality of frequency ranges; capturing said response time record ofeach one of said plurality of frequency ranges of said one non-inductiveshunt under test; transforming said response time record of each one ofsaid plurality of frequency ranges to said frequency domain; normalizingeach response time record of each one of said plurality standardizedfrequency ranges to said known non-inductive shunt value and said highrange root mean square current level; recording said response timerecord of each one of said plurality of standardized frequency rangestransformed to said frequency domain and normalized to saidnon-inductive shunt value as a plurality of calibration records;exciting said device under test at one of said plurality of standardizedfrequency ranges at said high range root mean square current level;capturing said response time record of said device under test at saidone of said plurality of standardized frequency ranges at said highrange root mean square current level; transforming said response timerecord of said device under test at said one of said plurality ofstandardized frequency ranges at said high range root mean squarecurrent level selecting one of said plurality of calibration recordscorresponding to said one of said plurality of standardized frequenciesused to excite said device under test; scaling said measurement rootmean squared current level; and applying said one of said plurality ofcalibration records to said response time record of said device undertest; and generating said measurement of said device under test.
 4. Themethod of claim 3, wherein said plurality of frequency ranges compriseharmonic octave and exact subsets of said frequency range.
 5. The methodof claim 4, wherein said harmonic octave subsets comprise exact harmonicoctave subsets of said frequency.
 6. The method of claim 1, furthercomprising in negative creating said response time record including anegative time portion backward of time zero corresponding to a fractionof a period of a lowest frequency of said excitation signal; anddiscarding said negative time portion of said response time record. 7.The method of claim 6, wherein said fraction of said period of saidlowest frequency comprises about ten percent of said period of saidlowest frequency.
 8. The method of claim 1, further comprising:examining said response time record; determining time periods in saidresponse time record where a voltage level exceeds a saturation level ofa digitizer within a data acquisition system; discarding said timeperiods in said response time record where said voltage level exceedssaid saturation level of said digitizer; discarding said time periods insaid calibration record which correspond to said time periods discardedin said response time record; applying resulting said calibration recordto resulting said time response record; and generating a measurement ofsaid device under test.